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EL5166, EL5167
Data Sheet November 17, 2005 FN7365.4
1.4GHz Current Feedback Amplifiers with Enable
The EL5166 and EL5167 amplifiers are of the current feedback variety and exhibit a very high bandwidth of 1.4GHz at AV = +1 and 800MHz at AV = +2. This makes these amplifiers ideal for today's high speed video and monitor applications, as well as a number of RF and IF frequency designs. With a supply current of just 8.5mA and the ability to run from a single supply voltage from 5V to 12V, these amplifiers offer very high performance for little power consumption. The EL5166 also incorporates an enable and disable function to reduce the supply current to 13A typical per amplifier. Allowing the CE pin to float or applying a low logic level will enable the amplifier. The EL5167 is offered in the 5-pin SOT-23 package and the EL5166 is available in the 6-pin SOT-23 as well as the industry-standard 8-pin SO packages. Both operate over the industrial temperature range of -40C to +85C.
Features
* Gain-of-1 bandwidth = 1.4GHz/gain-of-2 bandwidth = 800MHz * 6000V/s slew rate * Single and dual supply operation from 5V to 12V * Low noise = 1.5nV/Hz * 8.5mA supply current * Fast enable/disable (EL5166 only) * 600MHz family - (EL5164 and EL5165) * 400MHz family - (EL5162 and EL5163) * 200MHz family - (EL5160 and EL5161) * Pb-free plus anneal available (RoHS compliant)
Applications
* Video amplifiers * Cable drivers * RGB amplifiers * Test equipment * Instrumentation * Current to voltage converters
Pinouts
EL5166 (8-PIN SO) TOP VIEW
NC 1 IN- 2 IN+ 3 VS- 4 + 8 CE 7 VS+ 6 OUT 5 NC
EL5166 (6-PIN SOT-23) TOP VIEW
OUT 1 VS- 2 IN+ 3 +6 VS+ 5 CE 4 IN-
EL5167 (5-PIN SOT-23, SC-70) TOP VIEW
OUT 1 VS- 2 IN+ 3 +4 IN5 VS+
1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright Intersil Americas Inc. 2003-2005. All Rights Reserved All other trademarks mentioned are the property of their respective owners.
EL5166, EL5167 Ordering Information
PART NUMBER EL5166IS EL5166IS-T7 EL5166IS-T13 EL5166ISZ (See Note) EL5166ISZ-T7 (See Note) EL5166ISZ-T13 (See Note) EL5166IW-T7 EL5166IW-T7A EL5166IWZ-T7 (See Note) EL5166IWZ-T7A (See Note) EL5167IC-T7 EL5167IC-T7A EL5167ICZ-T7 (See Note) EL5167ICZ-T7A (See Note) EL5167IW-T7 EL5167IW-T7A EL5167IWZ-T7 (See Note) EL5167IWZ-T7A (See Note) PACKAGE 8-Pin SO 8-Pin SO 8-Pin SO 8-Pin SO (Pb-free) 8-Pin SO (Pb-free) 8-Pin SO (Pb-free) 6-Pin SOT-23 6-Pin SOT-23 6-Pin SOT-23 (Pb-free) 6-Pin SOT-23 (Pb-free) 5-Pin SC-70 5-Pin SC-70 5-Pin SC-70 (Pb-free) 5-Pin SC-70 (Pb-free) 5-Pin SOT-23 5-Pin SOT-23 5-Pin SOT-23 (Pb-free) 5-Pin SOT-23 (Pb-free) TAPE & REEL 7" 13" 7" 13" 7" (3K pcs) 7" (250 pcs) 7" (3K pcs) 7" (250 pcs) 7" (3K pcs) 7" (250 pcs) 7" (3K pcs) 7" (250 pcs) 7" (3K pcs) 7" (250 pcs) 7" (3K pcs) 7" (250 pcs) PKG. DWG. # MDP0027 MDP0027 MDP0027 MDP0027 MDP0027 MDP0027 MDP0038 MDP0038 MDP0038 MDP0038 P5.049 P5.049 P5.049 P5.049 MDP0038 MDP0038 MDP0038 MDP0038
NOTE: Intersil Pb-free products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020.
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FN7365.4 November 17, 2005
EL5166, EL5167
Absolute Maximum Ratings (TA = 25C)
Supply Voltage between VS+ and VS- . . . . . . . . . . . . . . . . . . . 12.6V Slewrate between VS+ and VS- . . . . . . . . . . . . . . . . . . . . . . . . 1V/s Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 50mA IOUT . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 200mA I into VIN+, VIN-, Enable Pins . . . . . . . . . . . . . . . . . . . . . . . . . 4mA Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves Pin Voltages. . . . . . . . . . . . . . . . . . . . . . . . . VS- -0.5V to VS+ +0.5V Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65C to +150C Ambient Operating Temperature . . . . . . . . . . . . . . . .-40C to +85C Die Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . 125C
CAUTION: Stresses above those listed in "Absolute Maximum Ratings" may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
Electrical Specifications
PARAMETER AC PERFORMANCE BW -3dB Bandwidth
VS+ = +5V, VS- = -5V, RF = 392 for AV = 1, RF = 250 for AV = 2, RL = 150, TA = 25C Unless Otherwise Specified. CONDITIONS MIN TYP MAX UNIT
DESCRIPTION
AV = +1 AV = +2
1400 800 100 4000 6000 8 1.7 19 50
MHz MHz MHz V/s ns nV/Hz pA/Hz pA/Hz %
BW1 SR tS eN iNiN+ dG dP
0.1dB Bandwidth Slew Rate 0.1% Settling Time Input Voltage Noise IN- Input Current Noise IN+ Input Current Noise Differential Gain Error (Note 1) Differential Phase Error (Note 1)
AV = +2 VO = -2.5V to +2.5V, AV = +2 VOUT = -2.5V to +2.5V, AV = -1
AV = +2 AV = +2
0.01 0.03
DC PERFORMANCE VOS TCVOS ROL Offset Voltage Input Offset Voltage Temperature Coefficient Transimpedance Measured from TMIN to TMAX 0.5 -5 -0.5 3.52 1.1 2.5 5 mV V/C M
INPUT CHARACTERISTICS CMIR CMRR -ICMR +IIN -IIN RIN CIN Common Mode Input Range (guaranteed by CMRR test) Common Mode Rejection Ratio - Input Current Common Mode Rejection + Input Current - Input Current Input Resistance Input Capacitance 3 52 -1 -25 -25 50 3.3 57 0.7 0.7 8.5 130 1.5 66 1 25 25 250 V dB A/V A A k pF
OUTPUT CHARACTERISTICS VO Output Voltage Swing RL = 150 to GND RL = 1k to GND IOUT Output Current RL = 10 to GND 3.6 3.8 110 3.8 4.0 160 4.1 4.2 200 V V mA
3
FN7365.4 November 17, 2005
EL5166, EL5167
Electrical Specifications
PARAMETER SUPPLY ISON ISOFF+ ISOFFPSRR -IPSR Supply Current - Enabled Supply Current - Disabled Supply Current - Disabled Power Supply Rejection Ratio - Input Current Power Supply Rejection No load, VIN = 0V No load, VIN = 0V No load, VIN = 0V DC, VS = 4.75V to 5.25V DC, VS = 4.75V to 5.25V 7.5 1 -25 70 -0.5 8.5 4 -14 50 0.2 1 9.3 25 -1 mA A A dB A/V VS+ = +5V, VS- = -5V, RF = 392 for AV = 1, RF = 250 for AV = 2, RL = 150, TA = 25C Unless Otherwise Specified. (Continued) DESCRIPTION CONDITIONS MIN TYP MAX UNIT
ENABLE (EL5166 ONLY) tEN tDIS IIHCE IILCE VIHCE VILCE NOTE: 1. Standard NTSC test, AC signal amplitude = 286mV, f = 3.58MHz. Enable Time Disable Time CE Pin Input High Current CE Pin Input Low Current CE Input High Voltage for Power-down CE Input Low Voltage for Power-down CE = VS+ CE = VS1 VS+ -1 VS+ -3 170 1.25 0 13 -1 25 ns s A A V V
Typical Performance Curves
5 NORMALIZED MAGNITUDE (dB) 4 3 2 1 0 -1 -2 -3 -4 -5 100K 1M 10M RF=511 RF=608 RF=698 RF=806 RF=900 100M RF=1K 1G NORMALIZED MAGNITUDE (dB) VCC=5V VEE=-5V RL=150 RF=392 RF=662 4 3 2 1 0 -1 -2 -3 VCC=5V -4 VEE=-5V RL=150 -5 RF=392 -6 100K 1M RG=93 RG=392 RG=186 RF=368
RG=43 10M FREQUENCY (Hz) 100M 1G
FREQUENCY (Hz)
FIGURE 1. FREQUENCY RESPONSE AS THE FUNCTION OF RF
FIGURE 2. FREQUENCY RESPONSE AS THE FUNCTION OF THE GAIN
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FN7365.4 November 17, 2005
EL5166, EL5167 Typical Performance Curves (Continued)
5 NORMALIZED MAGNITUDE (dB) 4 3 2 1 0 -1 -2 -3 -4 -5 100K 1M 10M 100M 1G C=0p C=1p C=4.7p C=2.5p C=1.5p NORMALIZED GAIN (dB) 5 4 3 2 1 0 -1 -2 -3 -4 -5 100K 1M 10M 100M 1G FREQUENCY (Hz) FREQUENCY (Hz) C=0 C=1p VCC=+V VCC=+5V VEE=-5V VEE=-5V RL=150W RL=150 RF=RG=392 C=4.7p C=2.5p C=1.5p
FIGURE 3. FREQENCY RESPONSE vs CIN
FIGURE 4. NON-INVERTING FREQUENCY RESPONSE FOR VARIOUS CIN- (6-PIN SOT-23)
4 3 NORMALIZED GAIN (dB) 2 1 0 -1 -2 -3 -4 -5 -6 1M
VCC, VEE=5V RF=220 RG=220 0.5V/DIV 1G
RF=220 RG=100
10M
100M
2ns/DIV
FREQUENCY (Hz)
FIGURE 5. INVERTING FREQUENCY RESPONSE FOR GAIN OF 1 AND 2
FIGURE 6. RISE AND FALL TIME (6-PIN SOT-23)
4 3 NORMALIZED GAIN (dB) 2 1 0 -1 -2 -3 -4 -5 -6 100K 1M 10M 100M 1G 2.5V 3.0V RL=150 RF=300 RG=300
4 3 5.0V NORMALIZED GAIN (dB) 6.0V 2 1 0 -1 -2 -3 -4 -5 -6 1M 10M 100M 1K 6.0V 5.0V RL=150 RF=220 RG=220 2.5V 3.5V
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 7. FREQUENCY RESPONSE AS THE FUNCTION OF THE POWER SUPPLY VOLTAGE
FIGURE 8. INVERTING AMPLIFIER, FREQUENCY RESPONSE AS THE FUNCTION OF VCC, VEE GAIN - 1
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FN7365.4 November 17, 2005
EL5166, EL5167 Typical Performance Curves (Continued)
2.5V
5.0V 6.0V
VCC, VEE=2.5V 0 -90 10
VCC, VEE=5V GAIN=2
MAGNITUDE (dB)
100K PHASE () ZOUT () 1 10K 1K -270 100 100K 1M 10M 100M 1G 10m 10K 100K 1M FREQUENCY (Hz) 10M 100M
2.5V 5.0V -180
100m
FREQUENCY (Hz)
FIGURE 9. TRANSIMPEDANCE MAGNITUDE AND PHASE AS THE FUNCTION OF THE FREQUENCY
FIGURE 10. CLOSED LOOP OUTPUT IMPEDANCE vs FREQUENCY (6-PIN SOT-23)
PSRR (VCC) (dB)
PSRR (VEE) (dB)
VCC=5V 10 VEE=-5V RL=150 20 RF=402 RG=402 30 40 50 60 70 80 100 1K 10K 100K 1M 10M 100M FREQUENCY (Hz)
0
0 10 20 30 40 50 60 70 80
VCC=5V VEE=-5V RL=150 RF=402 RG=402
100
1K
10K
100K
1M
10M
100M
FREQUENCY (Hz)
FIGURE 11. PSRR +5V
FIGURE 12. PSRR -5V
0 -10 -20 CMRR (dB) -30 -40 -50 -60 -70 -80 1K 10K 100K 1M 3.5V 10M 100M 300M 2.5V 6.0V 5.0V RF=RG=250 NORMALIZED MAGNITUDE (dB)
3 2 1 0 -1 -2 -3 -4 -5 -6 -7 FREQUENCY (Hz) VCC=5V VEE=-5V RL=150 GAIN=2 LOAD=150 INPUT LEVEL=3VP-P 100K 1M 10M 100M 1G
FREQUENCY (Hz)
FIGURE 13. COMMON MODE REJECTION AS THE FUNCTION OF THE FREQUENCY AND POWER SUPPLY VOLTAGE
FIGURE 14. LARGE SIGNAL RESPONSE
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FN7365.4 November 17, 2005
EL5166, EL5167 Typical Performance Curves (Continued)
2
-50 VCC, VEE = 6V 5V DISTORTION (dB) -60 -65 -70 -75 -80 SECOND HARMONIC -55
VCC, VEE=5V, RL=150, AV=2
1.5 VOUTP-P (V)
THD
1 2.5V 0.5
3V
THIRD HARMONIC
0 100 200 300 400 500 600 700 800 900 1000 FREQUENCY (Hz)
-85
1
6
11
16
21
26
31
36
FREQUENCY (MHz)
FIGURE 15. TOUT vs FREQUENCY AND VCC, VEE
FIGURE 16. DISTORTION vs FREQUENCY
-74 -76 DISTORTION (dB) -78 -80 -82 -84 -86 THD HD2 HD3
f=1MHz, RL=150, AV=2, VOP-P=2V DISTORTION (dB)
10 0 -10 -20 -30 -40 -50 -60 -70 -80 -90 HD3 5 6 7 8 9
f=5MHz, RL=150, AV=2, VO=2VP-P
THD HD2
5
6
7
8
9
10
11
12
10
11
12
TOTAL SUPPLY VOLTAGE (V)
TOTAL SUPPLY VOLTAGE (V)
FIGURE 17. HARMONIC DISTORTION vs SUPPLY VOLTAGE
FIGURE 18. HARMONIC DISTORTION vs SUPPLY VOLTAGE
-50 -55 DISTORTION (dB) -60 -65 -70 -75 -80 -85 -90 SECOND HARMONIC
-50 f=10MHz, RL=150, AV=2 VO=2VP-P THD -55 DISTORTION (dB) -60 -65 -70 -75 -80 5 6 7 8 9 10 11 12 THIRD HARMONIC 5 6 7 8
f=20MHz, RL=150, AV=2 VO=2VP-P
THD SECOND HARMONIC
THIRD HARMONIC
9
10
11
12
TOTAL SUPPLY VOLTAGE (V)
TOTAL SUPPLY VOLTAGE (V)
FIGURE 19. DISTORTION vs POWER SUPPLY VOLTAGE
FIGURE 20. DISTORTION vs POWER SUPPLY VOLTAGE (EL5166)
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FN7365.4 November 17, 2005
EL5166, EL5167 Typical Performance Curves (Continued)
FIGURE 21. TURN ON TIME (EL5166)
FIGURE 22. TURN OFF TIME (EL5166)
8.5 8.4 8.2 8.1 8 7.9 7.8 7.7 7.6 7.5 7.4 2.5 3 3.5 4 4.5 5 5.5 6 ISPOWER DISSIPATION (W) SUPPLY CURRENT (mA) 8.3 IS
1.4 1.2 1 0.8 0.6 0.4 0.2 0
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD
909mW SO8 JA=110C/W 435mW
SOT23-5/6 JA=230C/W 0 25 50 75 85 100 125 150
SUPPLY VOLTAGE (V)
AMBIENT TEMPERATURE (C)
FIGURE 23. SUPPLY CURRENT vs SUPPLY VOLTAGE (EL5166)
FIGURE 24. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
1 0.9 POWER DISSIPATION (W) 0.8
JEDEC JESD51-3 LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD
0.7 625mW 0.6 0.5 0.4 0.3 0.2 0.1 0 0 SOT23-5/6 JA=256C/W 25 50 75 85 100 125 150 391mW SO8 JA=160C/W
AMBIENT TEMPERATURE (C)
FIGURE 25. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
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FN7365.4 November 17, 2005
EL5166, EL5167 Pin Descriptions
8-PIN SO 1, 5 2 4 4 6-PIN SOT-23 5-PIN SOT-23 PIN NAME NC INFUNCTION Not connected Inverting input
VS+
EQUIVALENT CIRCUIT
IN+
IN-
VSCIRCUIT 1
3 4 6
3 2 1
3 2 1
IN+ VSOUT
Non-inverting input Negative supply Output
(See circuit 1)
VS+
OUT
VSCIRCUIT 2
7 8
6 5
5
VS+ CE
Positive supply Chip enable
VS+
CE
VSCIRCUIT 3
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FN7365.4 November 17, 2005
EL5166, EL5167 Applications Information
Product Description
The EL5166 and EL5167 are current-feedback operational amplifiers that offers a wide -3dB bandwidth of 1.4GHz and a low supply current of 8.5mA per amplifier. The EL5166 and EL5167 work with supply voltages ranging from a single 5V to 10V and they are also capable of swinging to within 1V of either supply on the output. Because of their currentfeedback topology, the EL5166 and EL5167 do not have the normal gain-bandwidth product associated with voltagefeedback operational amplifiers. Instead, their -3dB bandwidth remains relatively constant as closed-loop gain is increased. This combination of high bandwidth and low power, together with aggressive pricing make the EL5166 and EL5167 ideal choices for many low-power/highbandwidth applications such as portable, handheld, or battery-powered equipment.
Capacitance at the Inverting Input
Any manufacturer's high-speed voltage- or current-feedback amplifier can be affected by stray capacitance at the inverting input. For inverting gains, this parasitic capacitance has little effect because the inverting input is a virtual ground. But for non-inverting gains, this capacitance (in conjunction with the feedback and gain resistors) creates a pole in the feedback path of the amplifier. This pole, if low enough in frequency, has the same destabilizing effect as a zero in the forward open-loop response. The use of large value feedback and gain resistors exacerbates the problem by further lowering the pole frequency (increasing the possibility of oscillation). The EL5166 and EL5167 frequency responses are optimized with the resistor values in Figure 3. With the high bandwidth of these amplifiers, these resistor values might cause stability problems when combined with parasitic capacitance, thus ground plane is not recommended around the inverting input pin of the amplifier.
Power Supply Bypassing and Printed Circuit Board Layout
As with any high frequency device, good printed circuit board layout is necessary for optimum performance. Low impedance ground plane construction is essential. Surface mount components are recommended, but if leaded components are used, lead lengths should be as short as possible. The power supply pins must be well bypassed to reduce the risk of oscillation. The combination of a 4.7F tantalum capacitor in parallel with a 0.01F capacitor has been shown to work well when placed at each supply pin. For good AC performance, parasitic capacitance should be kept to a minimum, especially at the inverting input. (See the Capacitance at the Inverting Input section) Even when ground plane construction is used, it should be removed from the area near the inverting input to minimize any stray capacitance at that node. Carbon or Metal-Film resistors are acceptable with the Metal-Film resistors giving slightly less peaking and bandwidth because of additional series inductance. Use of sockets, particularly for the SO package, should be avoided if possible. Sockets add parasitic inductance and capacitance which will result in additional peaking and overshoot.
Feedback Resistor Values
The EL5166 and EL5167 have been designed and specified at a gain of +2 with RF approximately 392. This value of feedback resistor gives 800MHz of -3dB bandwidth at AV = 2 with about 0.5dB of peaking. Since the EL5166 and EL5167 are current-feedback amplifiers, it is also possible to change the value of RF to get more bandwidth. As seen in the curve of Frequency Response for Various RF and RG, bandwidth and peaking can be easily modified by varying the value of the feedback resistor. Because the EL5166 and EL5167 are current-feedback amplifiers, their gain-bandwidth product is not a constant for different closed-loop gains. This feature actually allows the EL5166 and EL5167 to maintain reasonable constant -3dB bandwidth for different gains. As gain is increased, bandwidth decreases slightly while stability increases. Since the loop stability is improving with higher closed-loop gains, it becomes possible to reduce the value of RF below the specified 250 and still retain stability, resulting in only a slight loss of bandwidth with increased closed-loop gain.
Disable/Power-Down
The EL5166 amplifier can be disabled placing its output in a high impedance state. When disabled, the amplifier supply current is reduced to 13A. The EL5166 is disabled when its CE pin is pulled up to within 1V of the positive supply. Similarly, the amplifier is enabled by floating or pulling its CE pin to at least 3V below the positive supply. For 5V supply, this means that an EL5166 amplifier will be enabled when CE is 2V or less, and disabled when CE is above 4V. Although the logic levels are not standard TTL, this choice of logic voltages allows the EL5166 to be enabled by tying CE to ground, even in 5V single supply applications. The CE pin can be driven from CMOS outputs. 10
Supply Voltage Range and Single-Supply Operation
The EL5166 and EL5167 have been designed to operate with supply voltages having a span of greater than 5V and less than 10V. In practical terms, this means that the EL5166 and EL5167 will operate on dual supplies ranging from 2.5V to 5V. With single-supply, they will operate from 5V to 10V. As supply voltages continue to decrease, it becomes necessary to provide input and output voltage ranges that can get as close as possible to the supply voltages. The EL5166 and EL5167 have an input range which extends to within 1.8V of either supply. So, for example, on 5V supplies, the EL5166 and EL5167 have an input range
FN7365.4 November 17, 2005
EL5166, EL5167
which spans 3.2V. The output range of the EL5166 and EL5167 is also quite large, extending to within 1V of the supply rail. On a 5V supply, the output is therefore capable of swinging from -4V to +4V. about 25, it is important to calculate the maximum junction temperature (TJMAX) for the application to determine if power supply voltages, load conditions, or package type need to be modified for the EL5166 and EL5167 to remain in the safe operating area. These parameters are calculated as follows:
T JMAX = T MAX + ( JA x n x PD MAX )
Video Performance
For good video performance, an amplifier is required to maintain the same output impedance and the same frequency response as DC levels are changed at the output. This is especially difficult when driving a standard video load of 150, because of the change in output current with DC level. Previously, good differential gain could only be achieved by running high idle currents through the output transistors (to reduce variations in output impedance.) These currents were typically comparable to the entire 8.5mA supply current of each EL5166 and EL5167 amplifier. Special circuitry has been incorporated in the EL5166 and EL5167 to reduce the variation of output impedance with current output. This results in dG and dP specifications of 0.01% and 0.03, while driving 150 at a gain of 2.
where: TMAX = Maximum ambient temperature JA = Thermal resistance of the package n = Number of amplifiers in the package PDMAX = Maximum power dissipation of each amplifier in the package PDMAX for each amplifier can be calculated as follows:
V OUTMAX PD MAX = ( 2 x V S x I SMAX ) + ( V S - V OUTMAX ) x --------------------------R
L
Output Drive Capability
In spite of their low 8.5mA of supply current, the EL5166 and EL5167 are capable of providing a minimum of 110mA of output current. With so much output drive, the EL5166 and EL5167 are capable of driving 50 loads to both rails, making them an excellent choice for driving isolation transformers in telecommunications applications.
where: VS = Supply voltage ISMAX = Maximum supply current of 1A VOUTMAX = Maximum output voltage (required) RL = Load resistance
Driving Cables and Capacitive Loads
When used as a cable driver, double termination is always recommended for reflection-free performance. For those applications, the back-termination series resistor will decouple the EL5166 and EL5167 from the cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without a back-termination resistor. In these applications, a small series resistor (usually between 5 and 50) can be placed in series with the output to eliminate most peaking. The gain resistor (RG) can then be chosen to make up for any gain loss which may be created by this additional resistor at the output. In many cases it is also possible to simply increase the value of the feedback resistor (RF) to reduce the peaking.
Current Limiting
The EL5166 and EL5167 have no internal current-limiting circuitry. If the output is shorted, it is possible to exceed the Absolute Maximum Rating for output current or power dissipation, potentially resulting in the destruction of the device.
Power Dissipation
With the high output drive capability of the EL5166 and EL5167, it is possible to exceed the 125C Absolute Maximum junction temperature under certain very high load current conditions. Generally speaking when RL falls below 11
FN7365.4 November 17, 2005
EL5166, EL5167 Typical Application Circuits
0.1F +5V IN+ INVS+ EL5166 OUT +5V IN+ 5 250 0.1F +5V IN+ INVS+ EL5166 OUT 5 VIN VOUT 250 +5V IN+ INVS+ EL5166 OUT INVS+ EL5166 OUT 250 250 0.1F
VS0.1F 250
-5V
VS0.1F
-5V
0.1F
VS0.1F 250
VOUT
-5V VIN 250 -5V
VS0.1F
FIGURE 26. INVERTING 200mA OUTPUT CURRENT DISTRIBUTION AMPLIFIER
FIGURE 27. FAST-SETTLING PRECISION AMPLIFIER
0.1F +5V IN+ INVS+ EL5166 OUT IN+5V IN+
0.1F
VS+ EL5166
OUT
VS0.1F 250 120 0.1F VOUT+ 1k 240 VS+ EL5166
VS0.1F 250
-5V
-5V 250
0.1F +5V IN+ IN-5V VIN 250 250 OUT 120
0.1F +5V
0.1F VOUT1k
IN+ IN-
VS+ EL5166
VS0.1F
OUT
VOUT
VS0.1F 250 RECEIVER
-5V 250
TRANSMITTER
FIGURE 28. DIFFERENTIAL LINE DRIVER/RECEIVER
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FN7365.4 November 17, 2005
EL5166, EL5167 SO Package Outline Drawing
13
FN7365.4 November 17, 2005
EL5166, EL5167 SOT-23 Package Outline Drawing
14
FN7365.4 November 17, 2005
EL5166, EL5167 SC-70 Package Outline Drawing
D
P5.049
VIEW C
e1
5 LEAD SMALL OUTLINE TRANSISTOR PLASTIC PACKAGE INCHES MILLIMETERS MIN 0.80 0.00 0.80 0.15 0.15 0.08 0.08 1.85 1.80 1.15 MAX 1.10 0.10 1.00 0.30 0.25 0.22 0.20 2.15 2.40 1.35 6 6 3 3 4 NOTES -
5 E 1 2 3
4 C L C L E1
SYMBOL A A1 A2 b b1
MIN 0.031 0.000 0.031 0.006 0.006 0.003 0.003 0.073 0.071 0.045
MAX 0.043 0.004 0.039 0.012 0.010 0.009 0.009 0.085 0.094 0.053
e
C L 0.20 (0.008) M C L C
b
c c1
C
D E E1
A
A2
A1
SEATING PLANE -C-
e e1 L L1
0.0256 Ref 0.0512 Ref 0.010 0.018
0.65 Ref 1.30 Ref 0.26 0.46
0.017 Ref. 0.006 BSC 0o 5 0.004 0.004 0.010 8o
0.420 Ref. 0.15 BSC 0o 5 0.10 0.15 0.25 8o
0.10 (0.004) C
L2
WITH PLATING c b b1 c1
5
N R R1 NOTES:
Rev. 2 9/03
BASE METAL
1. Dimensioning and tolerances per ASME Y14.5M-1994.
4X 1 R1 R GAUGE PLANE SEATING PLANE C L1 4X 1 VIEW C L
2. Package conforms to EIAJ SC70 and JEDEC MO-203AA. 3. Dimensions D and E1 are exclusive of mold flash, protrusions, or gate burrs. 4. Footlength L measured at reference to gauge plane. 5. "N" is the number of terminal positions. 6. These Dimensions apply to the flat section of the lead between 0.08mm and 0.15mm from the lead tip. 7. Controlling dimension: MILLIMETER. Converted inch dimensions are for reference only.
L2
NOTE: The package drawing shown here may not be the latest version. To check the latest revision, please refer to the Intersil website at
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation's quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com 15
FN7365.4 November 17, 2005

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